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TS613
DUAL WIDE BAND OPERATIONAL AMPLIFIER WITH HIGH OUTPUT CURRENT
s LOW NOISE : 3nV/Hz, 1.2pA/Hz s HIGH OUTPUT CURRENT : 200mA s VERY LOW HARMONIC AND INTERMODULATION DISTORTION
s HIGH SLEW RATE : 40V/s s SPECIFIED FOR 25 LOAD
DESCRIPTION The TS613 is a dual operational amplifier featuring a high output current (200mA min.), large gain-bandwidth product (130MHz) and capable of driving a 25 load with a 160mA output current at 6V power supply. This device is particularly intended for applications where multiple carriers must be amplified simultaneously with very low intermodulation products. The TS613 is housed in a SO8 package. APPLICATION
D SO-8 (Plastic Micropackage)
PIN CONNECTIONS (top view)
s UPSTREAM line driver for Assymetric Digital
Subscriber Line (ADSL) (NT). ORDER CODE
Package Part Number TS613ID Temperature Range D -40, +85C *
D = Small Outline Package (SO) - also available in Tape & Reel (DT)
May 2000
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TS613
ABSOLUTE MAXIMUM RATINGS
Symbol VCC Vid Vin Toper Tstd Tj Rthjc R tha P max. Supply voltage 1) Differential Input Voltage Input Voltage Range
3) 2)
Parameter
Value 7 2 6 -40 to + 85 -65 to +150 150 28 175 715
4)
Unit V V V C C C C/W C/W mW
Operating Free Air Temperature Range TS612ID Storage Temperature Maximum Junction Temperature Thermal Resistance Junction to Case Thermal Resistance Junction to Ambient Area Maximum Power Dissipation (@25C) Output Short Circuit Duration
1. All voltages values, except differential voltage are with respect to network terminal. 2. Differential voltages are non-inverting input terminal with respect to the inverting input terminal. 3. The magnitude of input and output voltages must never exceed VCC +0.3V.
4. An output current limitation protects the circuit from transient currents. Short-circuits can cause excessive heating. Destructive dissipation can result from short circuit on amplifiers.
OPERATING CONDITIONS
Symbol VCC Vicm Supply Voltage Common Mode Input Voltage Parameter Value 2.5 to 6 (VCC) +2 to (V CC+) -1 Unit V V
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TS613
ELECTRICAL CHARACTERISTICS.
Symbol Parameter
VCC = 6V, Tamb = 25C (unless otherwise specified).
Test Conditi on Tamb Tmin. < Tamb < Tmax. Tamb = 25C Tamb Tmin. < Tamb < Tmax. Tamb Tmin. < Tamb < Tmax. Vic = 2V to 2V, Tamb Tmin. < Tamb < Tmax. Vic = 6V to 4V, T amb Tmin. < Tamb < Tmax. No load, Vout = 0 Iout = 160mA, RL to GND Iout = 160mA, RL to GND Vout = 7V peak RL = 25, Tamb Tmin. < Tamb < Tmax. AVCL = +11, f = 20MHz RL = 100 AVCL = +7, RL = 50 Vic = 6V, Tamb Tmin. < Tamb < Tmax. Vic = 6V, Tamb Tmin. < Tamb < Tmax. RL = 25//15pF RL = 25//15pF f = 100kHz f = 100kHz Vout = 4Vpp, f = 100kHz AVCL = -10 RL = 25//15pF Vout = 4Vpp, f = 100kHz AVCL = -10 Load =25//15pF Vout = 4Vpp, f = 100kHz AVCL = +2 Load =25//15pF Vout = 4Vpp, f = 100kHz AVCL = +2 Load =25//15pF F1 = 80kHz, F2 = 70kHz Vout = 8Vpp, AVCL = -10 Load = 25//15pF F1 = 80kHz, F2 = 70kHz Vout = 8Vpp, AVCL = -10 Load = 25//15pF 60 40 3 1.2 -69 4 90 70 70 50 88 11 4.5 -4.5 11000 15 5 108 Min. -6 Typ. -1 Max 6 10 6 0.2 3 5 15 30 Unit
DC PERFORMANCE
Vio V io Iio Iib CMR SVR ICC VOH VOL AVD GBP SR Iout Isink Isource M14 M6 en in THD Input Offset Voltage Differential Input Offset Voltage Input Offset Current Input Bias Current Common Mode Rejection Ratio Supply Voltage Rejection Ratio Total Supply Current per Operator High Level Output Voltage Low Level Output Voltage Large Signal Voltage Gain mV mV A A dB dB mA V V V/V
DYNAMIC PERFORMANCE
-4
6500 5000 80 23 +200 +180
Gain Bandwidth Product Slew Rate Output Short Circuit Current Output Sink Current Output Source Current Phase Margin at A VCL = 14dB Phase Margin at A VCL = 6dB Equivalent Input Noise Voltage Equivalent Input Noise Current Total Harmonic Distorsion
130 40 320
MHz V/s mA mA -200 -180 mA nV/Hz pA/Hz dB
NOISE AND DISTORTION
HD2-10
2nd Harmonic Distorsion
-70
dBc
HD2 +2
2nd Harmonic Distorsion
-74
dBc
HD3 +2
3rd Harmonic Distorsion
-79
dBc
IM2-10
2nd Order Intermodulation Product
-77
dBc
IM3-10
3rd Order Intermodulation Product
-77
dBc
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TS613
INTERMODULATION DISTORTION The curves shown below are the measurements results of a single operator wired as an adder with a gain of 15dB. The operational amplifier is supplied by a symmetric 6V and is loaded with 25. Two synthesizers (Rhode & Schwartz SME) generate two frequencies (tones) (70 & 80kHz ; 180 & 280kHz). An HP3585 spectrum analyzer measures the spurious level at different frequencies. The curves are traced for different output levels (the value in the X ax is the value of each tone). The output levels of the two tones are the same. The generators and spectrum analyzer are phase locked to enhance measurement precision. 3rd ORDER INTERMODULATION Gain=15dB, Vcc=6V, RL=25, 2 tones 70kHz/ 80kHz 3rd ORDER INTERMODULATION Gain=15dB, Vcc=6V, RL=25, 2 tones 180kHz/ 280kHz
0 -10 -20
0 -10 -20 -30
IM3 (dBc)
-30
IM3 (dBc)
-40 -50 -60 -70 -80 -90 -100 1
-40 -50 -60 -70 -80
80kHz 380kHz
90kHz 230kHz
60kHz 220kHz
1,5 2 2,5 3 3,5 4 4,5
640kHz 740kHz
-90 -100 1 1,5 2 2,5
3
3,5
4
4,5
Vout peak (V)
Vout peak (V)
2nd ORDER INTERMODULATION Gain=15dB, Vcc=6V, RL=25, 2 tones 180kHz/ 280kHz, Spurious measurement @100kHz
-55
IM2 (dBc)
-60
-65
-70 1,5 2 2,5 3 3,5 4 4,5
Vout peak (V)
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TS613
Closed Loop Gain and Phase vs. Frequency Gain=+2, Vcc=6V, RL=25 Closed Loop Gain and Phase vs. Frequency Gain=+6, Vcc=6V, RL=25
10
200
20
200
Gain
15 0 100 Phase (degrees) 10
Gain
100 Phase (degrees)
Gain (dB)
-10
Phase
Gain (dB)
5 0 -5
0
Phase
0
-20
-100
-10 -15
-100
-30
-200
-20
-200
10kHz
100kHz
1MHz
10MHz
100MHz
10kHz
100kHz
1MHz
10MHz
100MHz
Frequency
Frequency
Closed Loop Gain and Phase vs. Frequency Gain=+11, Vcc=6V, RL=25
Equivalent Input Voltage Noise Gain=+100, Vcc=6V, no load
30
200
20
Gain
20 100
15 en (nV/VHz)
+ _
10k
10
Phase
0 0
Phase (degrees)
Gain (dB)
10
100
-10 -20 -30
-100
5
-200
0 100Hz 1kHz 10kHz 100kHz 1MHz Frequency
10kHz
100kHz
1MHz 10MHz Frequency
100MHz
Maximum Output Swing Vcc=6V, RL=25
Channel Separation (Xtalk) vs. Frequency XTalk=20Log(V2/V1), Vcc=6V, RL=25
5 4 3 2
-20
VIN
output
-30 -40 -50 -60 -70 -80
+ 4 9.9 _
V1
1k 25
100
swing (V)
1 0 -1 -2 -3 -4 -5 0 2
input
Xtalk (dB)
+ 4 9.9 _
V2
1k 25
100
4
6
8
10
10kHz
100kHz
1MHz
10MHz
Time (s)
Frequency
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TYPICAL APPLICATION : TS613 AS DRIVER FOR ADSL LINE INTERFACES
A SINGLE SUPPLY IMPLEMENTATION WITH PASSIVE OR ACTIVE IMPEDANCE MATCHING
by C. PRUGNE
ADSL CONCEPT Asymmetric Digital Subscriber Line (ADSL), is a new modem technology, which converts the existing twisted-pair telephone lines into access paths for multimedia and high speed data communications. ADSL transmits more than 8 Mbps to a subscriber, and can reach 1Mbps from the subscriber to the central office. ADSL can literally transform the actual public information network by bringing movies, television, video catalogs, remote CD-ROMs, LANs, and the Internet into homes. An ADSL modem is connected to a twisted-pair telephone line, creating three information channels: a high speed downstream channel (up to 1.1MHz) depending on the implementation of the ADSL architecture, a medium speed upstream channel (up to 130kHz) and a POTS (Plain Old Telephone Service), split off from the modem by filters. THE LINE INTERFACE - ADSL Remote Terminal (RT): The Figure1 shows a typical analog line interface used for ADSL. The upstream and downstream signals are separated from the telephone line by using an hybrid circuit and a line transformer. On this note, the accent will be made on the emission path. Figure 1 : Typical ADSL Line Interface
high output current
digital to emission LPfilter analog (analog)
The TS613 is used as a dual line driver for the upstream signal. For the remote terminal it is required to create an ADSL modem easy to plug in a PC. In such an application, the driver should be implemented with a +12 volts single power supply. This +12V supply is available on PCI connector of purchase. The figure 2 shows a single +12V supply circuit that uses the TS613 as a remote terminal transmitter in differential mode. Figure 2 : TS613 as a differential line driver with a +12V single supply
1 100n 3 +12V 1k 2 8
+ _
+12V
1
12.5
10n
Vi
47k
R1
R2
1:2 Vo 25
Hybrid & Transformer
100
Vi
1k
10
47k 100n 6 5
_
R3
12.5
Vo
7
GND
+
GND 4
100n
upstream impedance matching
HYBRID CIRCUIT
digital treatment
TS613 Line Driver
analog to digital
reception (analog)
reception circuits
twisted-pair telephone line
downstream
The driver is biased with a mid supply (nominaly +6V), in order to maintain the DC component of the signal at +6V. This allows the maximum dynamic range between 0 and +12 V. Several options are possible to provide this bias supply (such as a virtual ground using an operational amplifier), such as a two-resistance divider which is the cheapest solution. A high resistance value is required to limit the current consumption. On the other hand, the current must be high enough to bias the inverting input of the TS613. If we consider this bias current (5A) as the 1% of the current through the resistance divider (500A) to keep a stable mid supply, two 47k resistances can be used. The input provides two high pass filters with a break frequency of about 1.6kHz which is necessary to remove the DC component of the input signal. To avoid DC current flowing in the primary of the transformer, an output capacitor is used. The
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TS613
1F capacitance provides a path for low frequencies, the 10nF capacitance provides a path for high end of the spectrum. In differential mode the TS613 is able to deliver a typical amplitude signal of 18V peak to peak. The dynamic line impedance is 100. The typical value of the amplitude signal required on the line is up to 12.4V peak to peak. By using a 1:2 transformer ratio the reflected impedance back to the primary will be a quarter (25) and therefore the amplitude of the signal required with this impedance will be the half (6.2 V peak to peak). Assuming the 25 series resistance (12.5 for both outputs) necessary for impedance matching, the output signal amplitude required is 12.4 V peak to peak. This value is acceptable for the TS613. In this case the load impedance is 25 for each driver. For the ADSL upstream path, a lowpass filter is absolutely necessary to cutoff the higher frequencies from the DAC analog output. In this simple non-inverting amplification configuration, it will be easy to implement a Sallen-Key lowpass filter by using the TS613. For ADSL over POTS, a maximum frequency of 135kHz is reached. For ADSL over ISDN, the maximum frequency will be 276kHz. INCREASING THE LINE LEVEL BY USING AN ACTIVE IMPEDANCE MATCHING With passive matching, the output signal amplitude of the driver must be twice the amplitude on the load. To go beyond this limitation an active maching impedance can be used. With this technique it is possible to keep good impedance matching with an amplitude on the load higher than the half of the ouput driver amplitude. This concept is shown in figure3 for a differential line. Figure 3 : TS613 as a differential line driver with an active impedance matching
1 100n 3 +12V 1k 2
+ _
Component calculation: Let us consider the equivalent circuit for a single ended configuration, figure4. Figure 4 : Single ended equivalent circuit
+
Rs1 Vi
_
R2
Vo
Vo
-1
R3
1/2R1 1/2 RL
Let us consider the unloaded system. Assuming the currents through R1, R2 and R3 as respectively:
2V i ( V i - V o ) (Vi + Vo) -------- , --- ---------------------- and ----------------------R1 R2 R3
As Vo equals Vo without load, the gain in this case becomes :
2R 2 R2 1 + ---------- + -----V o ( noload ) R1 G = ------------------------ - = ------------------------ R3 --------------Vi R2 1 - -----R3
The gain, for the loaded system will be (1):
2R 2 R2 1 + ---------- + -----1 R 1 R3 V o ( wi t hl oad ) ---------GL = --------------------------------- = -- ------------------------ - ,( 1 ) 2 R2 Vi 1 - -----R3
As shown in figure5, this system is an ideal generator with a synthesized impedance as the internal impedance of the system. From this, the output voltage becomes:
V o = ( V i G) - ( R oIout ) ,( 2 )
with Ro the synthesized impedance and Iout the output current. On the other hand Vo can be expressed as:
2R 2 R2 V i 1 + ---------- + --- - -- R 1 R3 R s1 Iout ------V o = --------------------------------------------- - -------------- ,( 3 ) R2 R2 1 - -------1 - --- R3 R3
8
+12V
1
12.5
10n
Vi
47k
R2
Vo Vo 25 Vo Vo
7
1:2
Hybrid & Transformer
R1
R3 R5
100
Vi
1k
1 0
47k 100n 6 5
_
R4
GND
12.5
+
100n
4
GND
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TS613
By identification of both equations (2) and (3), the synthesized impedance is, with Rs1=Rs2=Rs:
Rs R o = ---------------- ,( 4 ) R2 1 - -----R3
GL (gain for the loaded system) R1 R2 (=R4) R3 (=R5) Rs
GL is fixed for the application requirements GL=Vo/Vi=0.5(1+2R2/R1+R2/R3)/(1-R2/R3) 2R2/[2(1-R2/R3)GL-1-R2/R3] Abritrary fixed R2/(1-Rs/0.5RL) 0.5RL(k-1)
Figure 5 : Equivalent schematic. Ro is the synthesized impedance
CAPABILITIES
Ro Iout
Vi.Gi
1/2RL
The table below shows the calculated components for different values of k. In this case R2=1000 and the gain=16dB. The last column displays the maximum amplitude level on the line regarding the TS613 maximum output capabilities (18Vpp diff.) and a 1:2 line transformer ratio.
Active matching TS613 Output Level to get 12.4Vpp on the line (Vpp diff) 8 8.7 9.3 9.9 10.5 12.4
Unlike the level Vo required for a passive impedance, Vo will be smaller than 2Vo in our case. Let us write Vo=kVo with k the matching factor varying between 1 and 2. Assuming that the current through R3 is negligeable, it comes the following resistance divider:
k V oR L R o = ------------------------R L + 2R s1
k
R1 () 820 490 360 270
R3 () 1500 1600 2200 2400
Rs () 3.9 5.1 6.2 7.5
Maximum Line level (Vpp diff) 27.5 25.7 25.3 23.7 22.3 18
1.3 1.4 1.5 1.6 1.7
After choosing the k factor, Rs will equal to 1/2RL(k-1). A good impedance matching assumes:
1 R o = -- R L ,( 5 ) 2
240 3300 9.1 Passive matching
From (4) and (5) it becomes:
2R s R2 -------- - = 1 - --- - , ( 6 ) --RL R3
By fixing an arbitrary value for R2, (6) gives:
R2 R3 = -----------------2R s 1 - --------RL
MEASUREMENT OF THE POWER CONSUMPTION IN THE ADSL APPLICATION Conditions: Passive impedance matching Transformer turns ratio: 2 Maximun level required on the line: 12.4Vpp Maximum output level of the driver: 12.4Vpp Crest factor: 5.3 (Vp/Vrms) The TS613 power consumption during emission on 900 and 4550 meter twisted pair telephone lines: 360mW
Finally, the values of R2 and R3 allow us to extract R1 from (1), and it comes:
2R 2 R 1 = --------------------------------------------------------- ,( 7) 1 - R2 GL - 1 - R 2 2 --- ------- R3 R3
with GL the required gain.
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TS613
PACKAGE MECHANICAL DATA 8 PINS - PLASTIC MICROPACKAGE (SO)
Millimeters Dim. Min. A a1 a2 a3 b b1 C c1 D E e e3 F L M S 0.1 0.65 0.35 0.19 0.25 4.8 5.8 1.27 3.81 3.8 0.4 4.0 1.27 0.6 8 (max.) 0.150 0.016 Typ. Max. 1.75 0.25 1.65 0.85 0.48 0.25 0.5 45 (typ.) 5.0 6.2 0.189 0.228 Min. 0.004 0.026 0.014 0.007 0.010
Inches Typ. Max. 0.069 0.010 0.065 0.033 0.019 0.010 0.020 0.197 0.244 0.050 0.150 0.157 0.050 0.024
Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibil ity for the consequences of use of such information nor for any infring ement of patents or other righ ts of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject to change witho ut notice. This publ ication supersedes and replaces all information previously supplied. STMicroelectronics products are not authorized for use as critical components in life suppo rt devices or systems withou t express written approval of STMicroelectronics. (c) The ST logo is a registered trademark of STMicroelectronics (c) 2000 STMicroelectronics - Printed in Italy - All Rights Reserved STMicroelectronics GROUP OF COMPANIES Australia - Brazil - China - Finland - France - Germany - Hong Kong - India - Italy - Japan - Malaysia - Malta - Morocco Singapore - Spain - Sweden - Switzerland - United Kingdom (c) http://www. st.com
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